Circuit device, oscillator, electronic apparatus, and vehicle

ABSTRACT

A circuit device includes a control voltage input terminal to which a control voltage is inputted, an A/D conversion circuit A/D-converting the control voltage to generate control voltage data and A/D-converting a temperature detection voltage from a temperature sensor to generate temperature detection data, a processing circuit generating temperature compensation data of an oscillation frequency based on the temperature detection data and performing addition processing of the temperature compensation data and the control voltage data to generate frequency control data of the oscillation frequency, and an oscillation signal generation circuit generating an oscillation signal of the oscillation frequency set by the frequency control data, using the frequency control data and a resonator.

The present application is based on, and claims priority from JPApplication Serial Number 2018-082716, filed Apr. 24, 2018, thedisclosure of which is hereby incorporated by reference herein in itsentirety.

BACKGROUND 1. Technical Field

The present disclosure relates to a circuit device, an oscillator,electronic apparatus, a vehicle and the like.

2. Related Art

In related art, oscillators such as temperature compensated crystaloscillator (TCXO) and oven controlled crystal oscillator (OCXO) areknown. For example, JP-A-2013-146114 discloses a temperature compensatedcrystal oscillator which realizes an automatic frequency control (AFC)function by inputting an analog control voltage to an AFC circuit. InJP-A-2013-146114 and JP-A-2017-123631, when a control voltage other thana reference voltage is input to the AFC circuit, since a value of anequivalent capacitance on an oscillation circuit side changes, aconfiguration is disclosed in which an auxiliary second temperaturevoltage generation circuit is provided for correction thereof.

In addition, for example, JP-A-2017-123631 discloses a circuit devicewhich generates a low noise clock signal by disposing a terminal for adigital I/F and a terminal for a clock signal output along differentsides, respectively.

JP-A-2013-146114 and JP-A-2017-123631 are examples of the related art.

However, even when the configuration is disclosed in which the secondtemperature voltage generation circuit is provided according to thepresent disclosure described in JP-A-2013-146114, there is a case inwhich a correction error which cannot be ignored occurs due to avariation in an analog circuit or the like, so that there is a problemof not obtaining high precision frequency-temperature characteristics toa sufficient degree.

Further, in a circuit disposition of the circuit device described inJP-A-2017-123631, there is a problem in which a delay in data transferbetween an A/D conversion unit and a processing unit and a delay in datatransfer between the processing unit and an oscillation circuit mayincrease.

SUMMARY

An advantage of some aspects of the present disclosure is to solve anyor at least a part of the problems described above, and the presentdisclosure can be implemented as the following forms or aspects.

An aspect of the present disclosure relates to a circuit deviceincluding a control voltage input terminal to which a control voltage isinputted, an A/D conversion circuit A/D-converting the control voltageto generate control voltage data and A/D-converting a temperaturedetection voltage a temperature sensor to generate temperature detectiondata, a processing circuit generating temperature compensation data ofan oscillation frequency based on the temperature detection data andperforming addition processing of the temperature compensation data andthe control voltage data to generate frequency control data of theoscillation frequency, and an oscillation signal generation circuitgenerating an oscillation signal of the oscillation frequency set by thefrequency control data, using the frequency control data and aresonator.

In the circuit device according to the aspect of the present disclosure,the processing circuit may perform correction processing on additionresult data of the addition processing and output the frequency controldata after the correction processing, and the oscillation signalgeneration circuit may include a D/A conversion circuit D/A-convertingthe frequency control data after the correction processing andoutputting a capacitance control voltage, a variable capacitor of whicha capacitance may be controlled based on the capacitance controlvoltage, and an oscillation circuit oscillating the resonator with thecapacitance of the variable capacitor as a load capacitance to generatethe oscillation signal.

In the circuit device according to the aspect of the present disclosure,the processing circuit may perform conversion processing on the additionresult data of the addition processing and output division ratio data asthe frequency control data after the conversion processing, and theoscillation signal generation circuit may include an oscillation circuitoscillating the resonator to generate a second oscillation signal and afractional-N type PLL circuit having a dividing circuit in which adivision ratio may be set based on the division ratio data, comparingphases of a frequency division clock signal from the dividing circuitand the second oscillation signal, and generating the oscillationsignal.

In the circuit device according to the aspect of the present disclosure,the circuit device may have a first side, a second side opposite to thefirst side, a third side crossing the first side, and a fourth sideopposite to the third side. When a direction from the first side to thesecond side is defined as a first direction and a direction from thethird side to the fourth side is defined, as a second direction, theoscillation signal generation circuit may be disposed on the firstdirection side of the A/D conversion circuit, the processing circuit maybe disposed on the second direction side of the A/D conversion circuitand the oscillation signal generation circuit, the A/D conversioncircuit may be disposed at a position having a shorter distance from thefirst side compared to a distance from the second side, and theoscillation signal generation circuit may be disposed at a positionhaving a shorter distance from the second side compared to a distancefrom the first side.

In the circuit device according to the aspect of the present disclosure,a power supply circuit may be disposed between the A/D conversioncircuit and the oscillation signal generation circuit.

In the circuit device according to the aspect of the present disclosure,the power supply circuit may supply a first power supply voltage to theA/D conversion circuit, supply a second power supply voltage to theprocessing circuit, and supply a third power supply voltage to theoscillation signal generation circuit.

In the circuit device according to the aspect of the present disclosure,the circuit device may further include a memory storing data to be usedby the processing circuit, and the memory may be disposed between theprocessing circuit and the fourth side.

In the circuit device according to the aspect of the present disclosure,the circuit device may further include a digital interface terminalelectrically coupled to the processing circuit, and the digitalinterface terminal may be disposed between the processing circuit andthe fourth side

In the circuit device according to the aspect of the present disclosure,the circuit device may further include a buffer circuit buffering theoscillation signal and outputting the oscillation signal to an outside,and when an opposite direction of the second direction is defined as athird direction, the buffer circuit may be disposed on the thirddirection side of the oscillation signal generation circuit.

In the circuit device according to the aspect of the present disclosure,the circuit device may further include an oven control circuitcontrolling a temperature of the resonator, and when an oppositedirection of the second direction is defined as a third direction, theoven control circuit may be disposed on the third direction side of theA/D conversion circuit.

In the circuit device according to the aspect of the present disclosure,the circuit device may further include a PLL circuit generating andoutputting a clock signal obtained by multiplying the oscillationsignal, and when an opposite direction of the second direction isdefined as a third direction, the PLL circuit may be disposed on thethird direction side of the A/D conversion circuit.

Another aspect of the present disclosure relates to a circuit deviceincluding an A/D conversion circuit A/D-converting a temperaturedetection voltage from a temperature sensor to output temperaturedetection data, a processing circuit performing temperature compensationprocessing of an oscillation frequency based on the temperaturedetection data to generate and output frequency control data of theoscillation frequency, and an oscillation signal generation circuitgenerating an oscillation signal of the oscillation frequency set by thefrequency control data, using the frequency control data and aresonator. The circuit device has a first side, a second side oppositeto the first side, a third side crossing the first side, and a fourthside opposite to the third side. When a direction from the first side tothe second side is defined as a first direction and a direction from thethird side to the fourth side is defined as a second direction, theoscillation signal generation circuit is disposed on the first directionside of the A/D conversion circuit, the processing circuit is disposedon the second direction side of the A/D conversion circuit and theoscillation signal generation circuit, the A/D conversion circuit isdisposed at a position having a shorter distance from the first sidecompared to a distance from the second side, and the oscillation signalgeneration circuit is disposed at a position having a shorter distancefrom the second side compared to a distance from the first side.

Another aspect of the present disclosure relates to an oscillatorincluding the circuit device described above and the resonator.

Another aspect of the present disclosure relates to an electronicapparatus including a circuit device as described above.

Another aspect of the present disclosure relates to a vehicle includingthe circuit device as described above.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a first configuration example of a circuit device of a presentembodiment.

FIG. 2 is a second configuration example of the circuit device of thepresent embodiment.

FIG. 3 is an explanatory diagram of a problem of a configuration of acomparative example.

FIG. 4 is an explanatory graph of the problem of the configuration ofthe comparative example.

FIG. 5 is an operation explanatory diagram of the configuration of thecomparative example.

FIG. 6 is the operation explanatory diagram of the configuration of thecomparative example.

FIG. 7 is an operation explanatory diagram of the first configurationexample of the present embodiment.

FIG. 8 is an operation explanatory diagram of the second configurationexample of the present embodiment.

FIG. 9 shows a configuration example of fractional-N type PLL circuit.

FIG. 10 is a detailed configuration example ref the circuit device ofthe present embodiment.

FIG. 11 is a layout disposition example of a circuit device of thepresent embodiment.

FIG. 12 is a detailed layout disposition example of circuit device ofthe present embodiment.

FIG. 13 shows a configuration example of an oscillation circuit.

FIG. 14 is a configuration example of an oscillator.

FIG. 15 is a configuration example of electronic apparatus.

FIG. 16 is a configuration example of a vehicle.

DESCRIPTION OF EXEMPLARY EMBODIMENTS

Hereinafter, preferred embodiments of the present disclosure will bedescribed in detail. Note that the present embodiments described belowdo not unduly limit the contents of the present disclosure described inthe appended and all of the configurations described in presentembodiments are not indispensable as means for solving the presentdisclosure.

1. Configuration of Circuit Device

FIG. 1 shows a first configuration example of circuit device 20 of apresent embodiment. The circuit device 20 which is an integrated circuitdevice includes a control voltage input terminal TVC, an A/D conversioncircuit 40, a processing circuit 50, and an oscillation signalgeneration circuit 70. The circuit device 20 can also include atemperature sensor 30. Although the temperature sensor 30 isincorporated in the circuit device 20 in FIG. 1, the temperature sensor30 may be provided outside the circuit device 20. In this case, thecircuit device 20 may be provided with a temperature detection voltageinput terminal (not shown) to which a temperature detection voltage VTDfrom the external temperature sensor 30 is input. Alternatively, aconfiguration may be provided in which such a temperature detectionvoltage input terminal may be provided and the temperature sensor 30 maybe incorporated in the circuit device 20.

A control voltage VC is input to the control voltage input terminal TVC.The control voltage input terminal TVC can be realized by a pad of thecircuit device 20. The control voltage VC is a voltage for controllingan oscillation frequency of an oscillation signal OUT generated by theoscillation signal generation circuit 70 and is input to the circuitdevice 20 from an external controller or the like.

The temperature sensor 30 outputs a temperature dependent voltage whichchanges according to a temperature of an environment, as the temperaturedetection voltage VTD. The temperature of the environment is thetemperature of the environment surrounding, for example, the circuitdevice 20 and a resonator 10. For example, the temperature sensor 30generates the temperature dependent voltage using a circuit elementhaving temperature dependency, and outputs the temperature dependentvoltage based on a temperature independent voltage. For example, thetemperature sensor 30 outputs a forward voltage of a PN junction as thetemperature dependent voltage. The temperature independent voltage is,for example, a bandgap reference voltage or the like.

The A/D conversion circuit 40 generates control voltage data by A/Dconversion of the control voltage VC. Further, the A/D conversioncircuit 40 A/D-converts the temperature detection voltage VTD from thetemperature sensor 30 to generate temperature detection data. Thecontrol voltage data and the temperature detection data are output fromthe A/D conversion circuit 40 as A/D conversion data ADQ. The A/Dconversion circuit 40 may perform the A/D conversion of the controlvoltage VC and the A/D conversion of the temperature detection voltageVTD in a time division manner. Alternatively, a first A/D converter anda second A/D converter may be provided in the A/D conversion circuit 40,the A/D conversion of the control voltage VC may be performed by thefirst A/D converter, and the A/D conversion of the temperature detectionvoltage VTD may be performed by the second A/D converter. As an A/Dconversion method of the A/D conversion circuit 40, for example, asuccessive approximation type, a delta sigma type, a flash type, apipeline type, a double integral type or the like can be adopted.

The processing circuit 50 is a circuit that performs various digitalsignal processing. For example, the processing circuit 50 is a DSP thatperforms digital signal processing such as temperature compensationprocessing, aging correction processing, or digital filter processing.For example the processing circuit 50 can be realized by a processorsuch as a DSP and a CPU, or can be realized by an ASIC circuit byautomatic placement and routing such as a gate array.

For example, the processing circuit 50 performs various digital signalprocessing by a program running on the processor.

The processing circuit 50 of the present embodiment performs temperaturecompensation of an oscillation frequency based on the temperaturedetection data to generate frequency control data DFC of the oscillationfrequency. Specifically, the processing circuit 50 generates temperaturecompensation data of the oscillation frequency based on the temperaturedetection data. Then, the processing circuit 50 performs additionprocessing of the temperature compensation data and the control voltagedata, to generate the frequency control data DFC of the oscillationfrequency. The frequency control data DFC is also called a frequencycontrol code. That is, the processing circuit 50 performs thetemperature compensation processing of the oscillation frequency basedon the temperature detection data inputted as the A/D conversion dataADQ from the A/D conversion circuit 40. The temperature compensationprocessing is a compensation processing for making the oscillationfrequency constant with respect to a temperature change. Further, theprocessing circuit 50 performs addition processing of the controlvoltage data inputted as A/D conversion data ADQ from the A/D conversioncircuit 40, and the temperature compensation data generated by thetemperature compensation processing. That is, the control voltage dataand the temperature compensation data are digitally added. Then, theprocessing circuit 50 performs, for example, correction processing orconversion processing to be described later on addition result data ofthe addition processing, and outputs the frequency control data DFC tothe oscillation signal generation circuit 70 after the correctionprocessing or the conversion processing. The frequency control data DFCmay be generated by inputting the frequency control code (FCC) asfrequency control to the processing circuit 50. For example, the FCC isinput to the processing circuit 50 from an external processing devicevia a digital interface of the circuit device 20. The digital interfacecan be realized in, for example, a serial peripheral interface (SPI), aninter-integrated circuit (I2C), or the like.

The oscillation signal generation circuit 70 is a circuit, whichgenerates the oscillation signal OUT by using the resonator 10.

Specifically, the oscillation signal generation circuit 70 uses thefrequency control data DFC and the resonator 10, and generates theoscillation signal OUT of the oscillation frequency set by the frequencycontrol data DFC. For example, the oscillation signal generation circuit70 oscillates the resonator 10 at the oscillation frequency set by thefrequency control data DFC to generate the oscillation signal OUT.

Specifically, in the first configuration example of FIG. 1, theoscillation signal generation circuit 70 includes a D/A conversioncircuit 72, a variable capacitor 74, and an oscillation circuit 80. Inthis first configuration example, the processing circuit 50 performs thecorrection processing on the addition result data of the additionprocessing and outputs the frequency control data DFC after thecorrection processing. That is, the processing circuit 50 performs thecorrection processing on the addition result data of the control voltagedata and the temperature compensation data. This correction processingis, for example, correction processing for causing the oscillationfrequency of the oscillation signal OUT to linearly change with respectto a change of the control voltage VC. The D/A conversion circuit 72 ofthe oscillation signal generation circuit 70 D/A-converts the frequencycontrol data DFS after the correction processing and outputs acapacitance control voltage obtained by the D/A conversion to thevariable capacitor 74. A capacitance of the variable capacitor 74 iscontrolled based on a capacitance limit voltage. The variable capacitor74 is a capacitor whose capacitance value is variably controlled basedon the capacitance control voltage, and can be realized by a varactor orthe like which is a variable capacitance diode. The oscillation circuit80 oscillates the resonator 10 with the capacitance of the variablecapacitor 74 as a load capacitance, and generates the oscillation signalOUT.

Specifically, the circuit device 20 includes terminals T1 and T2 forcoupling of the resonator 10. These terminals T1 and T2 can be realizedby IC pads. The terminal T1 is coupled to one end of the resonator 10,and the terminal T2 is coupled to the other of the resonator 10. One endof the variable capacitor 74 is electrically coupled to the terminal T1.The other end of the variable capacitor 74 is grounded by theoscillation circus t 80, for example. Further, the other end of theresonator 10 is electrically coupled to the oscillation circuit 80 viathe terminal T2. An electrical coupling is that a coupling is made inwhich an electric signal can be transmitted, and is a coupling thatenables transmission of information by the electric signal. Theelectrical coupling may be, for example, a coupling a signal line, anactive element or the like.

The resonator 10 is an element that generates mechanical resonation byan electric signal. The resonator 10 can be realized by a resonatorelement such as a quartz crystal resonator element, for example. Forexample, the resonator 10 can be realized by the quartz crystalresonator element or the like which exhibits thickness-shear resonationwhose cut angle is AT cut, SC cut, or the like. For example, theresonator 10 may be a resonator built in a temperature compensatedoscillator (TCXO) not equipped with a thermostatic chamber, or aresonator built in a thermostatic chamber type oscillator (OCXO)equipped with the there static chamber. Further, the resonator 10 of thepresent embodiment can be realized by various resonator elements such asa resonator element of a type other than the thickness-shear resonationtype and a piezoelectric resonator element formed of a material otherthan quartz crystal. For example, a surface acoustic wave (SAW)resonator, a micro electro mechanical systems (MEMS) resonator as asilicon-based resonator formed using a silicon substrate, or the likemay be adopted as the resonator 10.

The D/A conversion circuit 72 performs D/A conversion of the frequencycontrol data DFC from the processing circuit 50 as described above. Thefrequency control data DFC inputted to the D/A conversion circuit 72 isfrequency control data after digital signal processing such astemperature compensation processing, aging correction processing, orKalman filter processing. As for a D/A conversion system of the D/Aconversion circuit 72, for example, a resistance string type which isalso called a resistance division type can be adopted. However, a D/Aconversion method is not limited to the type above, and various methodssuch as a resistance ladder type such as R-2R, a capacitance array type,a pulse width modulation type, or the like can be adopted. In additionto the D/A converter, the D/A conversion circuit 72 may include acontrol circuit thereof, a modulation circuit for performing dithermodulation, PWM modulation or the like, a filter circuit, or the like.

The variable capacitor 74 is realized by the varactor which is thevariable capacitance diode. The capacitance of the variable capacitor 74is variably controlled by the capacitance control voltage from the D/Aconversion circuit 72.

The oscillation circuit 80 has a buffer circuit for driving theresonator 10. As for the buffer circuit, for example, a bipolartransistor or the like can be used. For example, a current source isprovided between a collector of the bipolar transistor and a powersupply node on a high potential side. For example, one end of thevariable capacitor 74 is electrically coupled to one end of theresonator 10 via the terminal T1. The other end of the variablecapacitor 74 is electrically coupled to a GND node by the oscillationcircuit 80 and grounded, for example. The GND node is a ground node. Aterminal T2 to which the other end of the resonator 10 is coupled iselectrically coupled to, for example, a base of the bipolar transistorwhich is the buffer circuit of the oscillation circuit 80. In addition,the oscillation circuit 80 has a capacitor for load capacitance, one endof the capacitor is coupled to the terminal T2, and the other end of thecapacitor is electrically coupled to the GND node and grounded. Further,a feedback element such as a capacitor provided between the terminal T1and the terminal T2 may be provided in the oscillation circuit 80. Abase current generated by oscillation of the resonator 10 flows betweenthe base and an emitter of the bipolar transistor. Then, the oscillationsignal OUT is generated by using a collector current flowing between thecollector and the emitter of the bipolar transistor by the base current.The buffer circuit of the oscillation circuit 80 may be realized by aninverting amplifier circuit in which a node of the terminal T1 and onenode of nodes of the terminal T2 serve as input nodes and the other nodeof the terminal T2 serves as an output node. The inverting amplifiercircuit can be realized by, for example, an inverter circuit having acurrent control function.

FIG. 2 shows a second configuration example of the circuit device 20 ofthis present embodiment. In this second configuration example, theoscillation signal generation circuit 70 includes the oscillationcircuit 80 and a fractional-N type PLL circuit 82. The oscillationcircuit 80 oscillates the resonator 10 and outputs an oscillation signalOSCK. The oscillation signal OSCK is a second oscillation signal. Forexample, the resonator 10 is electrically coupled to the oscillationcircuit 80 via the terminals T1 and T2. Then, the resonator 10 is drivenby the buffer circuit provided in the oscillation circuit 80, toresonate the resonator 10 and to generate the oscillation signal OSCKwhich is output to the fractional-N type PLL circuit 82. Thefractional-N type PLL circuit 82 has a dividing circuit 83 and comparesphases of a frequency division clock signal from the dividing circuit 83and the oscillation signal OSCK, to generate the oscillation signal OUT.For example, in FIG. 2, the processing circuit 50 performs theconversion processing on the addition result data of the additionprocessing and outputs the frequency control data DFC after theconversion processing. Specifically, the processing circuit 50 convertsthe addition result data of the control voltage data and the temperaturecompensation data and outputs division ratio data as the frequencycontrol data DFC. The dividing circuit 83 of the fractional-N type PLLcircuit 82 sets the division ratio based on the division ratio datawhich is the frequency control data DFC, and outputs the frequencydivision clock signal of the oscillation signal OUT according to thedivision ratio. The fractional-N type PLL circuit 82 generates theoscillation signal OUT by comparing the phases of the frequency divisionclock signal and the oscillation signal OSCK from the oscillationcircuit 80.

FIG. 3 shows a configuration example of a circuit device of acomparative example. In FIG. 3, an analog control voltage VC isinputted, and a capacitance CV of a variable capacitor 75 is controlledbased on th control voltage VC. Further, based on a temperaturedetection voltage from the temperature sensor 30, a temperaturecompensation voltage generation circuit 32 outputs the temperaturecompensation voltage TC, and a capacitance CT of a variable capacitor 76is controlled based on the temperature compensation voltage. Thesecapacitances CV and CT become a load capacitance CL of the oscillationcircuit 80. An equivalent capacitance of the resonator 10 is set to C0.

In FIG. 3, one end of the variable capacitor 75 is coupled to one end ofthe resonator 10, and the other end of the variable capacitor 75 iscoupled to one end of the variable capacitor 76. The other end of thevariable capacitor 76 coupled to, for example, a GND node. For example,the variable capacitors 75 and 76 are coupled in series between one endof the resonator 10 and the GND node.

In the configuration of the comparative example, when a frequencyadjustment (AFC) using the control voltage VC is used in combinationwith the temperature compensation, a correction amount of thetemperature compensation is changed by the control voltage VC, and aproblem of deterioration of frequency-temperature characteristics mayoccur. In this case, although a method may be considered in which thetemperature compensation voltage is corrected while the control voltageVC is monitored, a correction error occurs, and it is difficult torealize high precision frequency-temperature characteristics.

For example, when the variable capacitor 75 for the frequency adjustmentand the variable capacitor 76 for the temperature compensation arecoupled in series between the resonator 10 and the GND node as shown inFIG. 3, a frequency deviation Δf of the oscillation signal OUT can beexpressed by the load capacitance CL and the equivalent capacitance C0of the resonator 10 as shown in the following formula (1). The frequencydeviation Δf represents a deviation of an actual frequency from anominal frequency.

Δf∝1/(C0+CL)   (1)

Further, the load capacitance CL can be expressed by the followingformula (2).

1/CL=1/CV+1/CT   (2)

The following formulas (3) and (4) are established according to theabove formulas (1) and (2).

Δf∝ERR×(1/CV+1/CT)   (3)

ERR=(CV×CT)/(C0×CV+C0×CT+CV×CT)   (4)

ERR corresponds to an error component. Further, for example, thefollowing relationships (5) and (6) are established between the controlvoltage VC and the capacitance CV of the variable capacitor 75 andbetween the temperature compensation voltage TC and the capacitance CTof the variable capacitor 76.

VC∝1/CV   (5)

TC∝1/CT   (6)

FIG. 4 shows a relationship between the temperature compensation voltageTC and the frequency deviation Δf in the configuration of thecomparative example. For example, assuming that the error component ERRis a constant, the following formula (7) is established from the aboveformulas (3), (5), and (6).

{f∝ERR×(VC+TC)   (7)

Therefore, when the control voltage VC is a constant, the frequencydeviation Δf is a linear function of the temperature compensationvoltage TC, and a linear relationship is established between thefrequency deviation Δf and the temperature compensation voltage TC. Thatis, in this case, the relationship between the temperature compensationvoltage TC and the frequency deviation Δf is in a linear relationship asindicated by characteristics of dotted lines described as “ideal” inFIG. 4. However, in reality, the error component ERR is not a constantbut a value corresponding to the capacitances CV and CT, and forexample, since the capacitance CT varies according to the temperaturecompensation voltage TC, the error component ERR also changes accordingto the temperature compensation voltage TC. As a result, as shown bydotted line characteristics in FIG. 4, a deviation occurs from an ideallinear relationship. Due to the deviation from the linear relationshipcaused by such an error component ERR, the problem of deterioration offrequency-temperature characteristics occurs. As a second comparativeexample of the present embodiment, it is conceivable to provide thevariable capacitor 75 for the frequency adjustment and the variablecapacitor 76 for the temperature compensation in parallel, between theresonator 10 and the GND node. However, in the second comparativeexample, since the frequency deviation is Δf∝1/(C0+CV+CT), the deviationfrom the ideal linear relationship is further increased as compared withthe configuration of the comparative example of FIG. 3, and thefrequency-temperature characteristics further deteriorate

FIG. 5 and FIG. 6 are diagrams explaining in detail the problem ofdeterioration of the frequency-temperature characteristics in theconfiguration of the comparative example. The temperature detectionvoltage VTD from the temperature sensor 30 changes as indicated by A1with respect to a temperature TMP. That is, the temperature detectionvoltage VTD is a temperature dependence voltage. The temperaturecompensation voltage generation circuit 32, to which the temperaturedetection voltage VTD is inputted, performs the temperature compensationas indicated by A2, and outputs the temperature compensation voltage TCto the variable capacitor 76. For example, when the temperaturecompensation is not performed, the frequency-temperature characteristicsof an oscillation frequency f has characteristics as indicated by A3.The temperature compensation voltage generation circuit 32 performs thetemperature compensation which cancels out the temperature dependency ofthe oscillation frequency f indicated by A3 by using coefficient datafor the temperature compensation. Accordingly, as indicated by A4, it ispossible to make the oscillation frequency f of the oscillation signalOUT constant with respect to a change of the temperature TMP.

On the other hand, the control voltage VC indicated by A5 is input tothe variable capacitor 75. The capacitance CV of the variable capacitor75 changes with respect to the control voltage VC as indicated by A6.The capacitance CT of the variable capacitor 76 also changes withrespect to the temperature compensation voltage TC, exhibiting a voltagecapacitance characteristic as indicated by A6. Further, the oscillationfrequency f changes with respect to the load capacitance CL, exhibitinga characteristic as indicated by A7. Therefore, ideally, the oscillationfrequency f changes linearly with respect to the control voltage VC asindicated by A8 in FIG. 5. That is, ideally, as indicated by A4, theoscillation frequency f can be controlled according to the controlvoltage VC, and the oscillation frequency f can be made constant withrespect to the change of the temperature TMP.

However, in reality, due to the error component ERR described in theabove formulas (3) and (4), the deviation from the ideal linearrelationship occurs in the frequency deviation Δf of the oscillationfrequency f as shown in FIG. 4. As a result, as indicated by B1 and B2in FIG. 6, the relationship between the control voltage VC and theoscillation frequency f does not become the linear relationshiprepresented by the linear function. Therefore, the change in theoscillation frequency f due to the control voltage VC does not become alinear change as indicated by A8 of FIG. 5, and thefrequency-temperature characteristics deteriorate. That is, when thecontrol voltage VC is changed, a frequency deviation as indicated by B2in FIG. 6 occurs, and there is a problem that the high precisionfrequency-temperature characteristics cannot be realized.

On the other hand, according to the circuit device 20 of the presentembodiments shown in FIGS. 1 and 2, the analog control voltage VCinputted from the outside is A/D-converted into the digital controlvoltage data by the A/D conversion circuit 40. In addition, thetemperature detection voltage VTD from the temperature sensor 30 is alsoA/D-converted into the digital temperature detection data by the A/Dconversion circuit 40. Then, the processing circuit 50 generates thetemperature compensation data of the oscillation frequency based on thetemperature detection data, performs the addition processing of thetemperature compensation data and the control voltage data, andgenerates the frequency control data DFC. Finally, the oscillationsignal OUT of the oscillation frequency set by the frequency controldata DFC is generated.

According to the circuit device 20 of the present embodiment having sucha configuration, it is unnecessary to separately provide the variablecapacitor 75 for the frequency adjustment and the variable capacitor 76for the temperature compensation as shown in the comparative example ofFIGS. 5 and 6. Therefore, an occurrence of a frequency error asindicated by B1 and B2 of FIG. 6 can be suppressed, and the highprecision frequency-temperature characteristics can be realized. Thatis, according to the circuit device 20 of the present embodiment, thetemperature compensation data and the control voltage data are digitallyadded in the processing circuit 50 to generate the frequency controldata DFC, and the oscillation signal OUT of the oscillation frequencyset by the frequency control data DFC is generated by the oscillationsignal generation circuit 70. Therefore, even if the variable capacitors75 and 76 are not separately provided as shown in FIGS. 5 and 6, it ispossible to perform the frequency adjustment and the temperaturecompensation by the control voltage VC, and it is possible to generatethe oscillation signal OUT with the high precision frequency-temperaturecharacteristics. Further, according to the circuit device 20 of thepresent embodiment, it is possible to have coexistence of the frequencyadjustment function by the analog control voltage VC with the digitaltemperature compensation. For example, even when the external processingdevice performs the frequency adjustment using the analog controlvoltage VC instead of the digital FCC, it is possible to handle thiscase, and convenience can be improved.

Specifically, in the first configuration example of FIG. 1, the additionprocessing of the temperature compensation data and the control voltagedata is performed to generate the frequency control data DFC, thefrequency control data DFC is D/A-converted to obtain the capacitancecontrol voltage, thereby the capacitance of the variable capacitor 74 iscontrolled, and an oscillation signal OUT is generated. Therefore, asshown in FIGS. 5 and 6, it is unnecessary to separately provide thevariable capacitor 75 for the frequency adjustment and the variablecapacitor 76 for the temperature compensation, and only one variablecapacitor 74 needs to be provided. This one capacitance of the variablecapacitor 74 is controlled by the capacitance control voltage, and theoscillation frequency of the oscillation circuit 80 is adjusted.Therefore, problems as indicated by B1 and B2 of FIG. 6 do not occur,and it is possible to generate the oscillation signal OUT with the highprecision frequency-temperature characteristics.

In the second configuration example of FIG. 2, the addition processingof the temperature compensation data and the control voltage data isperformed, and the division ratio data is generated as the frequencycontrol data DFC. The division ratio of the dividing circuit 83 is setby the division ratio data to generate the frequency division clocksignal, and the oscillation signal OUT is generated by the fractional-Ntype PLL circuit 82 based on the oscillation signal OSCK and thefrequency division clock signal. Accordingly, even if the variablecapacitors 75 and 76 as shown in FIGS. 5 and 6 are not provided, it ispossible to generate the oscillation signal OUT with high precisionfrequency-temperature characteristics, in which the frequency adjustmentby the control voltage VC and the temperature compensation by thetemperature sensor 30 are both performed.

FIG. 7 is a detailed operation explanatory diagram of the firstconfiguration example of FIG. 1. In FIG. 7, the processing circuit 50includes a temperature compensation unit 52, an adder 54, and acorrection processing unit 56. The temperature compensation unit 52performs the temperature compensation processing based on temperaturedetection data DTD from the A/D conversion circuit 40, and generates andoutputs the temperature compensation data DTC. The adder 54 performsaddition processing of control voltage data DVC from the A/D conversioncircuit 40 and the temperature compensation data DTC from thetemperature compensation unit 52, and outputs the addition result dataDFCI to the correction processing unit 56. The correction processingunit 56 performs correction processing for making a relationship of theoscillation frequency f with respect to the control voltage VC linear.The frequency control data DFC after the correction processing is inputto the D/A conversion circuit 72, and the load capacitance CL which isthe capacitance of the variable capacitor 74 is controlled based on thecapacitance control voltage from the D/A conversion circuit 72.

Specifically, the temperature detection voltage VTD from the temperaturesensor 30 changes as indicated by D1 with respect to the temperatureTMP. This temperature detection voltage VTD is A/D-converted into thetemperature detection data DTD by the AID conversion circuit 40. Thetemperature compensation unit 52, to which the temperature detectiondata DTD is inputted, performs the temperature compensation processingas indicated by D2, and generates the temperature compensation data DTC.Specifically, the temperature compensation unit 52 performs thetemperature compensation which cancels out the temperature dependency ofthe oscillation frequency f indicated by D3, by using the coefficientdata for the temperature compensation. Accordingly, as indicated by D4,it is possible to make the oscillation frequency f of the oscillationsignal OUT constant, with respect to the change of the temperature TMP.

On the other hand, the control voltage VC indicated by D5 isA/D-converted into the control voltage data DVC by the A/D conversioncircuit 40 as indicated by D6. The adder 54 performs addition processingof the control voltage data DVC and the temperature compensation dataDTC from the temperature compensation unit 52, and outputs the additionresult data DFCI. The correction processing unit 56 performs thecorrection processing on the addition result data DFCI as indicated byD7. Specifically, the correction processing unit 56 performs thecorrection processing so as to make the relationship of the oscillationfrequency f with respect to the control voltage VC linear, and outputsthe frequency control data DFC after the correction processing. Then,the D/A conversion circuit 72 performs the D/A conversion of thefrequency control data DFC and outputs the capacitance control voltageto the variable capacitor 74.

The load capacitance CD which is the capacitance of the variablecapacitor 74 changes with respect to the capacitance control voltagefrom the D/A conversion circuit 72, exhibiting a characteristic asindicated by D8. Further, the oscillation frequency f changes withrespect to the load capacitance CL, exhibiting the characteristic asindicated by D9. Accordingly, as indicated by D10, the oscillationfrequency f changes linearly with respect to the control voltage VC. Asa result, as indicated by D4, the oscillation frequency f can becontrolled according to the control voltage VC, and the oscillationfrequency f can be made constant with respect to the change of thetemperature TMP.

FIG. 8 is a detailed operation explanatory diagram of the secondconfiguration example of FIG. 2. In FIG. 8, the processing circuit 50includes a temperature compensation unit 52, an adder 54, and aconversion processing unit 57. The temperature compensation unit 52performs the temperature compensation processing on the temperaturedetection data DTD from the A/D conversion circuit 40, and generate: andoutputs the temperature compensation data DTC. The adder 54 performsaddition processing of the control voltage data DVC from the A/Dconversion circuit 40 and the temperature compensation data DTC from thetemperature compensation unit 52, and outputs the addition result dataDFCI to the conversion processing unit 57. The conversion processingunit 57 performs the conversion processing on the addition result dataDFCI and outputs division ratio data DIV as the frequency control dataDFC after the conversion processing. The division ratio based on thedivision ratio data DIV is set in the dividing circuit 83 of thefractional-N type PLL circuit 82. Then, the fractional-N type PLLcircuit 82 performs phase comparison between the frequency divisionclock signal from the dividing circuit 83 and the oscillation signalOSCK from the oscillation circuit 80, and generates the oscillationsignal OUT.

Specifically, the control voltage VC indicated by E1 is A/D-converted tothe control voltage data DVC by the A/D conversion circuit 40 asindicated by E2. The adder 54 performs addition processing of thecontrol voltage data DVC and the temperature compensation data DTC fromthe temperature compensation unit 52, and outputs the addition resultdata DFCI. The conversion processing unit 57 performs conversionprocessing on the addition result data DFCI as indicated by E2 andoutputs division ratio data DIV as the frequency control data DFC. Then,the division ratio based on the division ratio data DIV is set in thedividing circuit 83, so that the oscillation frequency f of theoscillation signal OUT changes according to the division ratio. As aresult, as indicated by E4, the oscillation frequency f can becontrolled according to the control voltage VC. Further, by performingthe temperature compensation by the temperature compensation unit 52,the oscillation frequency f can be made constant with respect to thechange of the temperature TMP.

FIG. 9 shows a configuration example of the fractional-N type PLLcircuit 82. The fractional-N type PLL circuit 82 includes the dividingcircuit 83, a phase comparator 84, a charge pump circuit 85, a low passfilter 86, a voltage control oscillation circuit 87, a clock generationcircuit 88, a delta-sigma modulation circuit 89, and an addition andsubtraction circuit 91. The phase comparator 84 compares phases of theoscillation signal OSCK which is the second oscillation signal from theoscillation circuit 80, and a frequency division clock signal FBCK fromthe dividing circuit 83. The charge pump circuit 85 converts a pulsevoltage outputted by the phase comparator 84 into a current. The lowpass filter 86 smooths the current outputted by the charge pump circuit85 and converts the current into a voltage. The voltage controloscillation circuit 87 outputs the oscillation signal OUT in which anoutput voltage of the low pass filter 86 is a control voltage and thecontrol voltage sets the oscillation frequency.

The dividing circuit 83 performs integer division on the oscillationsignal OUT outputted from the voltage control oscillation circuit 87,using an output signal of the addition and subtraction circuit 91 as aninteger division ratio, and outputs the frequency division clock signalFBCK.

The clock generation circuit 88 generates and outputs a clock signalDSMCK using the frequency division clock signal. FBCK. For example, theclock generation circuit 88 may buffer the frequency division clocksignal FBCK and output the clock signal DSMCK therefrom, or may outputthe clock signal DSMCK obtained by integer-dividing the frequencydivision clock signal FBCK.

The delta-sigma modulation circuit 89 synchronizes with the clock signalDSMCK from the clock generation circuit 88, and performs delta-sigmamodulation in which a fractional division ratio L/M is integrated andquantized. The addition and subtraction circuit 91 adds and subtracts adelta sigma modulation signal DMQ outputted from the delta-sigmamodulation circuit 89, and the integer division ratio N. An outputsignal of the addition and subtraction circuit 91 is input to a dividingcircuit 83. In the output signal of the addition and subtraction circuit91, a plurality of integer division ratios in a range around the integerdivision ratio N change in time series, and a time average value thereofcoincides with N+L/M. N+L/M is set by the division ratio data DIV fromthe processing circuit 50. For example, the oscillation frequency of theoscillation signal OUT is defined as f, and an oscillation frequency ofthe oscillation signal OSCK is defined as fosc. In this case, in asteady state in which a phase of the oscillation signal OSCK and a phaseof the frequency division clock signal FBCK are synchronized, thefollowing formula (8) is established.

f=(N+L/M)×fosc   (8)

By using the fractional-N type PLL circuit 82 having such aconfiguration, the oscillation signal OUT obtained by multiplying theoscillation signal OSCK by a division ratio expressed by N+L/M can begenerated.

FIG. 10 shows a detailed configuration example of the circuit device 20.In FIG. 10, in addition to the configurations of FIG. 1 and FIG. 2, abuffer circuit 90, a power supply circuit 100, a PLL circuit 110, anoven control circuit 120, and a memory 130 are further provided.

The buffer circuit 90 buffers and outputs the oscillation signal OUTfrom the oscillation signal generation circuit 70. For example, thebuffer circuit 90 outputs a signal obtained by buffering the oscillationsignal OUT as an oscillation signal FOUT, to the outside via a terminalTFOUT of the circuit device 20.

For example, the oscillation signal FOUT of a CMOS waveform isoutputted. Further, a clipped sine waveform may be outputted.

The power supply circuit 100 generates various power supply voltagesused in circuit device 20. For example, various power supply voltagesare generated based on an external power supply voltage inputted from apower supply terminal of the circuit device 20. For example, the powersupply circuit 100 supplies a power supply voltage V1 to the A/Dconversion circuit 40. The power supply circuit 100 supplies a powersupply voltage V2 to the processing circuit 50 and supplies a powersupply voltage V3 to the oscillation signal generation circuit 70. Thepower supply voltage V3 is also supplied to the buffer circuit 90, forexample. The power supply circuit 100 also supplies power supplyvoltages V4 and V5 to the PLL circuit 110 and the oven control circuit120. V1, V2, V3, V4, and V5 are a first power supply voltage, a secondpower supply voltage, a third power supply voltage, a fourth powersupply voltage, and a fifth power supply voltage, respectively. Forexample, the power supply circuit 100 has a plurality of regulatorcircuits, and supplies voltages obtained by regulating the externalpower supply voltage by these regulator circuits, as the power supplyvoltages V1 to V5. In this manner, by branching and supplying the powersupply voltage for each circuit block, power supply noise in one circuitblock can be suppressed from being transmitted to other circuit blocks,and stable circuit operation can be realized.

The PLL circuit 110 generates and outputs a clock signal CLK obtained bymultiplying the oscillation signal OUT. For example, the clock signalCLK, which is a frequency obtained by multiplying the frequency of theoscillation signal. OUT and is synchronized in phase with theoscillation signal OUT, is output to the outside via a clock outputterminal TCLK of the circuit device 20. As for the PLL circuit 110, forexample, the fractional-N type PLL circuit as shown in FIG. 9 can beused. By providing such a PLL circuit 110, for example, an appropriateclock signal CLK as a clock signal used for an RF circuit or the like ina base station system can be generated and supplied. Further, if such aPLL circuit 110 is provided, for example, phase noise in a low frequencybandwidth can be reduced by the oscillation signal generation circuit 70which is a clock signal generation circuit of a first stage, and phasenoise in a high frequency band can be reduced by the PLL circuit 110which is e clock signal generation circuit of a second stage.Accordingly, it is possible to generate the clean clock signal CLK withsmall phase noise in a wide frequency bandwidth ranging from the lowfrequency bandwidth to the high frequency bandwidth, and to supply theclean clock signal CLK by the RF circuit or the like of the basestation.

The oven control circuit 120 controls the temperature of the resonator10. For example, the oven control circuit 120 performs oven control ofthe oven type resonator 10 when the oven type resonator 10 provided inthe thermostatic chamber is used. For example, the oven control circuit120 performs the oven control of an oscillator by using a temperaturesensor for the oven control realized by thermistor or the like. Forexample, if a resistance value of the thermistor as the temperaturesensor changes according to an oven temperature of the oscillator, theoven control circuit 120 detects this change in the resistance value asa change in the temperature detection voltage. Then, a heater controlvoltage which changes according to the temperature detection voltage isgenerated and outputted via a terminal TOV for the oven control. Theheater control voltage is output to a heater provided in the oscillator.The heater is constituted with, for example, a heating power bipolartransistor which is a heating element, and a base voltage of the heatingpower bipolar transistor is controlled by the heater control voltage, sothat heating control of the heater is realized.

The memory 130 stores data used by the processing circuit 50.Specifically, the memory 130 stores the data used for the digital signalprocessing performed by the processing circuit 50. For example, when theprocessing circuit 50 performs the temperature compensation processing,the memory 130 stores the coefficient data for the temperaturecompensation. Further, when the processing circuit 50 performs the agingcorrection processing and the digital filter processing, the memory 130stores data for the aging correction and coefficient data for thedigital filter processing. The memory 130 can be realized by anonvolatile memory such as metal-oxide-nitride-oxide-silicon (MONOS) andEEPROM. Further, the memory 130 may be a memory serving as a work areaof the processing circuit 50. In this case, the memory 130 is realizedby SRAM or the like.

Further, the circuit device 20 includes a digital interface terminal TIFelectrically coupled to the processing circuit 50. The digital interfaceterminal TIF is a terminal for a digital interface circuit included inthe processing circuit 50. For example, the digital interface circuitcan be realized by an interface circuit of a two-wire inter-integratedcircuit (I2C) method. The I2C method is a synchronous serialcommunication method which communicates with two signal lines of aserial clock line and a bidirectional serial data line. In this case,the digital interface terminal TIF is a terminal to which the serialclock line and the serial data lines are coupled. A plurality of slavescan be coupled to a bus of the I2C, and a master designates individuallydetermined slave addresses, selects a slave, and then communicates withthe slave. Alternatively, the digital interface circuit may be realizedby an interface circuit of a 3-wire or 4-wire serial peripheralinterface (SPI) method. The SPI method is a synchronous serialcommunication method which communicates with the serial clock line andtwo unidirectional serial data lines. In this case, the digitalinterface terminal TIF is the terminal to which the serial clock lineand the serial data lines are coupled. A plurality of slaves can becoupled to the SPI bus, but in order to designate them, the master needsto select a slave using a slave select line and in this case, the slaveselect line is required.

2. Layout Disposition

FIG. 11 shows a layout disposition example of the circuit device 20 ofthe present embodiment. The circuit device 20 has sides SD1, SD2, SD3,and SD4. That is, the circuit device 20 includes the side SD1, the sideSD2 opposite to the side SD1, the side SD3 crossing the side SD1, andside SD4 opposite to the side SD3. A rectangular shape is formed bythese sides SD1, SD2, SD3 and SD4. The sides SD1, SD2, SD3, and SD4 area first side, a second side, a third side, and a fourth side,respectively. For example, the side SD1 and the side SD2 are sidesopposed to each other, and the sides SD3, and SD4 are orthogonal to thesides SD1 and SD2 and opposed to each other. A direction from the sideSD1 to the side SD2 is defined as DR1, and a direction from the side SD3to the side SD4 is defined as DR2. Further, an opposite direct of DR2 isdefined as DR3, and an opposite direction of DR1 is defined as DR4. Thedirections DR1, DR2, DR3, and DR4 are a first direction, a seconddirection, a third direction, and a fourth direction, respectively.

In this case, in FIG. 11, the oscillation signal generation circuit 70is disposed on the direction DR1 side which is the first direction sideof the A/D conversion circuit 40. The processing circuit 50 is disposedon the direction DR2 side which is the second direction side of the A/Dconversion circuit 40 and the oscillation signal generation circuit 70.The direction DR2 is a direction orthogonal to the direction DR1. Forexample, the A/D conversion circuit 40 and the processing circuit 50 aredisposed adjacent to each other along the direction DR2, and theoscillation signal generation circuit 70 and the processing circuit 50are also disposed adjacent to each other along the direction DR2.Disposition in which two circuit blocks are disposed adjacent to eachother means that no other circuit block is interposed between the twocircuit blocks in the disposition. Further, the A/D conversion circuit40 is disposed at a position having a shorter distance from the side SD1compared to a distance from the side SD2. On the other hand, theoscillation signal generation circuit 70 is disposed at a positionhaving a shorter distance from the side SD2 compared to a distance fromthe side SD1. For example, an area between a center line of the side SD1and the side SD2, and the side SD1 is defined as a first area, and anarea between the center line and the side SD2 is set as a second area.In this case, the A/D conversion circuit 40 is disposed in the firstarea on the side SD1 side and the oscillation signal generation circuit70 is disposed in the second area on the side SD2 side.

According to such a layout disposition, the A/D conversion data from theA/D conversion circuit 40 can be input to the processing circuit 50 viaa short-path wiring path. For example, the A/D conversion circuit 40A/D-converts the control voltage VC, outputs the control voltage dataDVC to the processing circuit 50, A/D-converts the temperature detectionvoltage VTD, and outputs the temperature detection data DTD to theprocessing circuit 50. By using the layout disposition shown in FIG. 11,the control voltage data DVC and the temperature detection data DTD canbe input to the processing circuit 50 via the short-path wiring path.The frequency control data DFC from the processing circuit 50 can alsobe input to the oscillation signal generation circuit 70 via theshort-path wiring path. For example, in the first configuration exampleof FIG. 1 and FIG. 7, it is possible to input the frequency control dataDFC from the processing circuit 50 to the D/A conversion circuit 72 viathe short-path wiring path and perform the D/A conversion. On the otherhand, in the second configuration example of FIGS. 2 and 8, thefrequency control data DFC from the processing circuit 50 can be inputto the dividing circuit 83 of the fractional-N type PLL circuit 82 viathe short-path wiring path, and the division ratio can be set.

As a result, the A/D conversion circuit 40, the processing circuit 50,and the oscillation signal generation circuit 70 can be compactly andefficiently laid out and disposed as shown in FIG. 11, and an area ofthe circuit device 20 can be reduced. It is also possible to minimize asignal delay of data transfer between the A/D conversion circuit 40 andthe processing circuit 50 and the signal delay of the data transferbetween the processing circuit 50 and the oscillation signal generationcircuit 70, and an occurrence of a defect in the circuit operation dueto the signal delay, or the like can be prevented.

In FIG. 11, the power supply circuit 100 is disposed between the A/Dconversion circuit 40 and the oscillation signal generation circuit 70.For example, the A/D conversion circuit 40 and the power supply circuit100 are disposed adjacent to each other along the direction DR1, and thepower supply circuit 100 and the oscillation signal generation circuit70 are also disposed adjacent to each other along the direction DR1.

With such a layout disposition, a space between the A/D conversioncircuit 40 and the oscillation signal generation circuit 70 can beeffectively utilized, and the power supply circuit 100 can be disposed.For example, since the processing circuit 50 which is a logic circuitperforms various digital signal processing, a circuit area thereofbecomes large. Therefore, when the processing circuit 50 is disposed onthe direction DR2 side of the A/D conversion circuit 40 and theoscillation signal generation circuit 70, there is a problem that anempty space is generated in an area of the direction DR3 side which isthe third direction side of the processing circuit 50, and an areabetween the A/D conversion circuit 40 and the oscillation signalgeneration circuit 70. In this respect, since the power supply circuit100 is disposed in the area in which the empty space is formed in FIG.11, the A/D conversion circuit 40, the processing circuit 50, theoscillation signal generation circuit 70, and the power supply circuit100 can be compactly and efficiently laid out and disposed, and the areaof the circuit device 20 can be further reduced.

As described in FIG. 10, the power supply circuit 100 supplies the powersupply voltage V1 to the A/D conversion circuit 40 and supplies thepower supply voltage V2 to the processing circuit 50. Further, the powersupply circuit 100 supplies the power supply voltage V3 to theoscillation signal generation circuit 70. For example, the power supplyvoltage V1 is supplied from the power supply circuit 100 to the A/Dconversion circuit 40 by a first power supply line wired along thedirection DR4. Further, the power supply voltage V2 is supplied from thepower supply circuit 100 to the processing circuit 50 by a second powersupply line wired along the direction DR2. Further, the power supplyvoltage V3 is supplied from the power supply circuit 100 to theoscillation signal generation circuit 70 by a third power supply linewired along the direction DR1. In this way, the power supply voltagesV1, V2, and V3 can be supplied from the power supply circuit 100 to theA/D conversion circuit 40, the processing circuit 50, and theoscillation signal generation circuit 70 by the first, second, and thirdpower supply lines having short wiring lengths.

For example, since the processing circuit 50 performs the digital signalprocessing at a high clock frequency, the digital signal processingcauses digital noise with a high noise level to occur. If the digitalnoise is transmitted to the A/D conversion circuit 40 and theoscillation signal generation circuit 70, a problem occurs in whichperformance of an analog circuit deteriorates, or the like. For example,problems occur in which an A/D conversion accuracy degrades, the digitalnoise with the high noise level is superimposed on an oscillationsignal, or the like. In this regard, in the present embodiment, thepower supply voltages V1 and V3 generated separately from the powersupply voltage V2 supplied to the processing circuit 50 are supplied tothe A/D conversion circuit 40 and the oscillation signal generationcircuit 70. For example, the power supply voltages V1 and V3 can besupplied to the A/D conversion circuit 40 and the oscillation signalgeneration circuit 70 by using the first power supply line and the thirdpower supply line which are different from the second power supply linewhich is from the power supply circuit 100 to the processing circuit 50.Therefore, the problem of the deterioration of the performance caused bythe digital noise of the processing circuit 50 can be prevented.

FIG. 12 shows a detailed layout disposition example of the circuitdevice of the present embodiment. As shown in FIG. 12, the circuitdevice 20 includes the memory 130 storing data which the processingcircuit 50 uses. As described with reference to FIG. 10, the memory 130stores the various coefficient data or the like used for the digitalsignal processing performed by the processing circuit 50. For example,the coefficient data for the temperature compensation processing, thecoefficient data for the digital filter processing, or the like arestored. The memory 130 is disposed between the processing circuit 50 andthe side SD4 of the circuit device 20. For example, in FIG. 12, thememory 130 is disposed corresponding to a position on a side of theprocessing circuit 50 on the side SD4 side. For example, the memory 130is disposed to overlap an I/O area along the side SD4.

According to such a layout disposition, the memory 130 can be disposedusing a space on the side of the processing circuit 50 on the SD4 side.For example, it is possible to dispose the memory 130 by effectivelyusing the space for the I/O area along the side SD4. Therefore, thememory 130 storing data used for the processing circuit 50 can beefficiently laid out and disposed, and scale of the circuit device 20can be reduced or the like. Further, the coefficient data or the likeread from the memory 130 can be inputted to the processing circuit 50through the short-path wiring path. Further, for example, when thememory 130 is a nonvolatile memory, a high voltage power supply forwriting and reading data is required, but it is also possible to disposea high voltage power supply terminal, for supplying the high voltagepower supply to the circuit device 20 from the outside, in the I/O areaalong the side SD4.

Further, the circuit device 20 includes the digital interface terminalTIF electrically coupled to the processing circuit 50. As described inFIG. 10, the digital interface terminal TIF is a clock terminal and adata terminal in the I2C and the SPI. As shown in FIG. 12, the digitalinterface terminal TIF is disposed between the processing circuit 50 andthe side SD4. For example, the digital interface terminal TIF isdisposed in the I/O area along the side SD4. For example, the A/Dconversion circuit 40, the power supply circuit 100, tie oscillationsignal generation circuit 70, the buffer circuit 90, or the like aredisposed on the direction DR3 side of the processing circuit 50, whilethe digital interface terminal TIF is disposed on the side of thedirection DR2 opposite to the direction DR3.

For example, in the digital interface terminal TIF, the digital noisewith the high noise level is generated by the clock signal or the datasignal of the I2C and the SPI. When the digital noise is transmitted tothe A/D conversion circuit 40, a problem such as degradation of the A/Dconversion accuracy is caused. Further, when the digital noise istransmitted to the oscillation signal generation circuit 70 and thebuffer circuit 90, the digital noise is superimposed on the oscillationsignal, causing problems such as degradation in accuracy of theoscillation frequency and increase in the phase noise. In this regard,in FIG. 12, the digital interface terminal TIF which is a source of thedigital noise is disposed between the processing circuit 50 and the sideSD4, and is disposed on the direction DR2 side of the processing circuit50. Therefore, the distance between the digital interface terminal TIFand the A/D conversion circuit 40 can be increased, and the distancebetween the digital interface terminal TIF, and the oscillation signalgeneration circuit 70 and the buffer circuit 90 can be increased.Therefore, the degradation of the A/D conversion accuracy due to thedigital noise can be suppressed. Further, the degradation of theaccuracy of the oscillation frequency and the increase of the phasenoise due to the digital noise can be suppressed.

The circuit device 20 also includes the buffer circuit 90 which buffersthe oscillation signal and outputs the signal to the outside. As shownin FIG. 12, the buffer circuit 90 is disposed on the direction DR3 sideof the oscillation signal generation circuit 70. For example, theoscillation signal generation circuit 70 is disposed on the directionDR3 side of the processing circuit 50, and the buffer circuit 90 isdisposed on the direction DR3 side of the oscillation signal generationcircuit. For example, the oscillation signal generation circuit 70 andthe buffer circuit 90 are disposed adjacent to each other along thedirection Specifically, in FIG. 12, he buffer circuit 90 is disposed ina corner area in which the side SD2 and the side SD3 cross each other.Further, the terminal TFOUT from which the oscillation signal isoutputted is disposed on the direction DR4 side of the buffer circuit 90in the I/O area along the side SD3.

According to such a layout disposition, the buffer circuit 90 outputtingthe oscillation signal can be disposed at a position which is a maximumdistance away from the processing circuit 50 and the digital interfaceterminal TIF. For example, the terminal TFOUT from which the oscillationsignal is outputted can be disposed in an area of the side SD3 opposedto an area of the side SD4 in which the digital interface terminal TIFis disposed. Accordingly, the digital noise generated in the processingcircuit 50 and the digital interface terminal TIF can be suppressed frombeing superimposed on the oscillation signal. Therefore, due to thedigital noise, an occurrence of the problems such as the degradation ofthe accuracy of the oscillation frequency and the increase of the phasenoise of the oscillation signal can be suppressed. Further, by disposingthe buffer circuit 90 so as to be adjacent to the direction DR3 side ofthe oscillation signal generation circuit 70, it is possible to couple asignal line with the oscillation signal from the oscillation signalgeneration circuit 70 to the buffer circuit 90 via a short path, anddegradation of performance caused by a parasitic capacitance of thesignal line or the like can be suppressed.

The resonator 10 of the present embodiment also includes the ovencontrol circuit 120 which controls the temperature of the resonator 10.As shown in FIG. 12, the oven control circuit 120 is disposed on thedirection DR3 side of the A/D conversion circuit 40. For example, inFIG. 12, the A/D conversion circuit 40 and the oven control circuit 120are disposed in the first area close to the side SD1 and in an area onthe direction DR3 side of the processing circuit 50, and the oscillationsignal generation circuit 70 and the buffer circuit 90 are disposed inthe second area close to the side SD2. In this way, the A/D conversioncircuit 40 and the oven control circuit 120, and the oscillation signalgeneration circuit 70 and the buffer circuit 90 can be disposed byeffectively utilizing a space on the direction DR3 side of theprocessing circuit 50. Accordingly, it is possible to enable anefficient layout disposition of these circuit blocks, and reduction inthe layout area of the circuit device 20, or the like can be realized.

The circuit device 20 also includes the PLL circuit 110 which generatesand outputs a clock signal obtained by multiplying the oscillationsignal. The PLL circuit 110 is disposed on the direction DR3 side of theA/D conversion circuit 40. For example, the PLL circuit 110 is disposedon the direction DR3 side of the A/D conversion circuit 40 and the powersupply circuit 100. Specifically, the PLL circuit 110 is disposedbetween the oven control circuit 120 and the buffer circuit 90. In thisway, the PLL circuit 110 can be disposed by effectively utilizing aspace on the direction DR3 side of the A/D conversion circuit 40.Further, for example, the PLL circuit 110 can be disposed on thedirection DR4 side of the oscillation signal generation circuit 70, andthe signal line with the oscillation signal from the oscillation signalgeneration circuit 70 can be coupled to the PLL circuit 110 via theshort path.

As described with reference to FIG. 10, the power supply circuit 100generates the power supply voltage V4 and supplies the voltage to thePLL circuit 110. For example, the power supply voltage V4 is suppliedfrom the power supply circuit 100 to the PLL circuit 110 via the fourthpower supply line wired along the direction DR3.

The PLL circuit 110 may also be the fractional-N type PLL circuit 82described in FIG. 9. For example, in a first operation mode of thecircuit device 20, the oscillation signal OUT is generated by the D/Aconversion circuit 72, the variable capacitor 74, and the oscillationcircuit 80 as in the first configuration example of FIG. 1. Then, asshown in FIG. 10, the PLL circuit 110 which is the fractional-N type PLLcircuit 82 generates and outputs the clock signal CLK obtained bymultiplying the oscillation signal OUT. In this case, the clock outputterminal. TCLK from which the clock signal CLK is outputted is disposedin the I/O area along the side SD3, for example. The control voltageinput terminal TVC to which the control voltage VC is inputted is alsodisposed in the I/O area along the side SD3. On the other hand, in asecond operation mode of the circuit device 20, an oscillation signalOUT is generated by the oscillation circuit 80 and the fractional-N typePLL circuit 82 which is the PLL circuit 110 as in the secondconfiguration example of FIG. 2. Accordingly, the operation of thecircuit device 20 in various operation modes is possible.

3. Oscillation Circuit

FIG. 13 shows a configuration example of the oscillation circuit 80.FIG. 13 shows an example of the oscillation circuit 80 of a Colpittstype. The variable capacitor 74 is provided between the node NA1 at oneend of the resonator 10 and the GND node. The node NA2 of the other endof the resonator 10 is coupled to a base of a bipolar transistor BTR. Aresistor RA1 is provided between a VDD node which is a power supply nodeon the high potential side and the collector of the bipolar transistorBTR, and a resistor RA2 is provided between the emitter of the bipolartransistor BTR and the GND node. A resistor RA3 is provided between theVDD node and the node NA2, and a resistor RA4 is provided between thenode NA2 and the GND node. Capacitors CA1 and CA2 are provided in seriesbetween the node NA2 and the GND node, and a filter FLT is providedbetween a coupling node NA3 of the capacitors CA1 and CA2 and a node NA4of the emitter of the bipolar transistor BTR. The oscillation circuit 80is not limited to the configuration of FIG. 13, and variousmodifications such as different coupling configurations are possible.Further, an oscillation circuit such as a Pierce type may be used as theoscillation circuit 80.

4. Oscillator

FIG. 14 shows a configuration example of an oscillator 400 including thecircuit device 20 of the present embodiment. As shown in FIG. 14, theoscillator 400 includes the resonator 10 and the circuit device 20. Theresonator 10 and the circuit device 20 are mounted in a package 410 ofthe oscillator 400. The terminal of the resonator 10 and the pad of theIC which is the terminal of the circuit device 20 are electricallycoupled by internal wiring of the package 410. In FIG. 14, theoscillator 400 is an oscillator of an oven structure. Specifically, theoscillator has a double oven structure.

The package 410 is constituted with a substrate 411 and a case 412.Various electronic components (not shown) are mounted on the substrate411. A second container 414 is provided inside the case 412, and a firstcontainer 413 is provided inside the second container 414. The resonator10 is mounted on an inner surface of an upper surface of the firstcontainer 413. Further, the circuit device 20, a heater 450, and atemperature sensor 460 of the present embodiment are mounted on an outersurface of the upper surface of the first container 413. The heater 450which is a heating element can adjust a temperature inside the secondcontainer 414, for example.

The temperature sensor 460 can detect the temperature inside the secondcontainer 414, for example.

The second container 414 is provided on a substrate 416. The substrate416 is a circuit substrate on which various electronic components can bemounted. A heater 452 and a temperature sensor 462 are mounted on a backside of a surface of the substrate 416 on which the second container 414is provided. For example, the heater 452 which is a heating element canadjust a temperature in a space between the case 412 and the secondcontainer 414. The temperature sensor 462 can detect the temperature inthe space between the case 412 and the second container 414.

As for heating elements of the heaters 450 and 452, for example, aheating power bipolar transistor, a heating heater MOS transistor, aheating resistor, a Peltier element or the like can be used. Control ofheating of the heaters 450 and 452 can be realized by the oven controlcircuit 120 of the circuit device 20, for example. A thermistor, adiode, or the like can be used as the temperature sensors 460 and 462,for example. In this way, FIG. 15, the temperature sensors 460 and 462are provided outside the circuit device 20, and the A/D conversioncircuit 40 A/D-converts the temperature detection voltage from theexternal temperature sensors 460 and 462. In this case, both thetemperature sensor 30 inside the circuit device 20 and the externaltemperature sensors 460 and may be used in combination. In FIG. 14,since temperature adjustment of the resonator 10 or the like can berealized in the thermostatic chamber having the double oven structure,it is possible to stabilize the oscillation frequency of the resonator10, or the like.

Although FIG. 14 shows the configuration example of the double ovenstructure, the oscillator 400 of the present embodiment is not limitedto such a configuration, and various modifications are possible. Forexample, the oscillator 400 may have a single oven structure. That is,in FIG. 14, although two containers are provided as the first and secondcontainers 413 and 414, the oscillator 400 may have the single ovenstructure in which one container is provided as the thermostaticchamber.

5. Electronic Apparatus and Vehicle

FIG. 15 shows a configuration example of electronic apparatus 500including the circuit device 20 of the present embodiment The electronicapparatus 500 includes the circuit device 20, the resonator 10, and aprocessing unit 520 of the present embodiment. The electronic apparatus500 can include an antenna ANT, a communication unit 510, an operationunit 530, a display unit 540, and a storage 550. The resonator 10 andthe circuit device 20 constitute the oscillator 400. Note that theelectronic apparatus 500 is riot limited to the configuration of FIG.15, and various modifications such as omitting some constituent elementsthereof and adding other constituent elements are possible.

The electronic apparatus 500 is, for example, a network-relatedapparatus such as a base station or a router, highly accuratemeasurement apparatus which measures physical quantities such asdistance, time, flow speed, or flow rate, biological informationmeasurement apparatus which measures biological information, in-vehicleapparatus, or the like. The biological information measurement apparatusis, for example, an ultrasonic measuring device, a pulse wave meter, ablood pressure measuring device or the like. The in-vehicle apparatus isapparatus for automatic operation, or the like. Further, the electronicapparatus 500 may be wearable apparatus such as a head mounted displaydevice and timepiece related apparatus, a portable information terminalsuch as a robot, a printing device, a projection device, and asmartphone, content providing apparatus which distributes content, orvideo apparatus such as a digital camera or a video camera, or the like.

The communication unit 510 which is a communication interface performsprocessing such as receiving data from the outside via the antenna ANTand transmitting the data to the outside. The processing unit 520 whichis a processor performs control processing of electronic apparatus 500,various digital processing of data transmitted and received via thecommunication unit 510, or the like. A function of the processing unit520 can be realized by a processor such as a microcomputer, for example.The operation unit 530 which is an operation interface is for a user toperform an input operation and can be realized by an operation button, atouch panel display, or the like. The display unit 540 displays varioustypes of information and can be realized by a display such as liquidcrystal and organic EL. The storage 550 stores data, and a functionthereof can be realized by a semiconductor memory such as RAM and ROM,HDD, or the like.

FIG. 16 shows an example of a vehicle including the circuit device 20 ofthe present embodiment. The circuit device 20 of the present embodimentcan be incorporated into various vehicles such as a car, an airplane, amotorcycle, a bicycle, or a ship. The vehicle is apparatus or a devicewhich includes a drive mechanism such as an engine and a motor, asteering mechanism such as a steering wheel and a rudder, and variouselectronic apparatus and which moves on the ground, the sky, and thesea. FIG. 16 schematically shows an automobile 206 as a specific exampleof the vehicle. The circuit device 20 of the present embodiment and anoscillator (not shown) having a resonator are incorporated in theautomobile 206. A control device 208 operates by a clock signalgenerated by the oscillator. The control device 208, for example,controls hardness of a suspension according to a position of a car body207, and controls brakes of individual wheels 209. For example,automatic operation of the automobile 206 may be realized by the controldevice 208. Note that apparatus incorporating the circuit device 20 andthe oscillator of the present embodiment is not limited to such acontrol device 208 but can be incorporated in various apparatus providedin the vehicle such as the automobile 206.

Although the present embodiment has been described in detail as above,it will be readily understood by those skilled in the art that manymodifications are possible that do not deviate practically from thenovel matters and effects of the present disclosure. Therefore, all suchmodifications are included in the scope of the present disclosure. Forexample, in the specification or the drawings, at least once, a termdescribed together with a different term which is broader or equivalentcan be replaced with the different term at any point in thespecification or the drawings. Further, all combinations of the presentembodiment and modifications are also included in the scope of thepresent disclosure. Further, the configuration and operation of thecircuit device, the electronic apparatus, and the vehicle, and the A/Dconversion processing, the temperature compensation processing, theaddition processing, the generation processing of the frequency controldata, the layout disposition of the circuit device, and the couplingconfiguration, or the like is not limited to those described in thepresent embodiment, and various modifications can be made.

The entire disclosure of Japanese Patent Application No. 2018-082716,filed Apr. 24, 2018 is expressly incorporated by reference herein.

What is claimed is:
 1. A circuit device comprising: an A/D conversioncircuit that receives a control voltage and generates control voltagedata, and receives a temperature detection voltage from a temperaturesensor and generates temperature detection data; a processing circuitthat generates temperature compensation data based on the temperaturedetection data, and generates frequency control data by performingaddition processing of the temperature compensation data and the controlvoltage data; and an oscillation signal generation circuit thatgenerates an oscillation signal of an oscillation frequency set by thefrequency control data, using the frequency control data and aresonator.
 2. The circuit device according to claim 1, wherein theprocessing circuit performs correction processing on addition resultdata of the addition processing and outputs the frequency control dataafter the correction processing, and the oscillation signal generationcircuit includes a D/A conversion circuit that receive the frequencycontrol data after the correction processing and output a capacitancecontrol voltage, a variable capacitor whose capacitance is controlledbased on the capacitance control voltage, and an oscillation circuitthat oscillates the resonator with the capacitance of the variablecapacitor as a load capacitance to generate the oscillation signal. 3.The circuit device according to claim 1, wherein the processing circuitperforms conversion processing on the addition result data of theaddition processing and outputs division ratio data as the frequencycontrol data after the conversion processing, and the oscillation signalgeneration circuit includes an oscillation circuit that oscillates theresonator to generate a second oscillation signal, and a fractional-Ntype PLL circuit having a dividing circuit in which a division ratio isset based on the division ratio data, comparing phases of a frequencydivision clock signal from the dividing circuit and the secondoscillation signal, and generating the oscillation signal.
 4. Thecircuit device according to claim 1, wherein the circuit device has afirst side, a second side opposite to the first side, a third sidecrossing the first side, and a fourth side opposite to the third side,and when a direction from the first side to the second side is definedas a first direction and a direction from the third side to the fourthside is defined as a second direction, the oscillation signal generationcircuit is disposed on the first direction side of the A/D conversioncircuit, the processing circuit is disposed on the second direction sideof the A/D conversion circuit and the oscillation signal generationcircuit, the A/D conversion circuit is disposed at a position having ashorter distance from the first side compared to a distance from thesecond side, and the oscillation signal generation circuit is disposedat a position having a shorter distance from the second side compared toa distance from the first side.
 5. The circuit device according to claim4, wherein a power supply circuit is disposed between the A/D conversioncircuit and the oscillation signal generation circuit
 6. The circuitdevice according to claim 5, wherein the power supply circuit supplies afirst power supply voltage to the A/D conversion circuit, supplies asecond power supply voltage to the processing circuit, and supplies athird power supply voltage to the oscillation signal generation circuit.7. The circuit device according to claim 4, further comprising a memorystoring data to be used by the processing circuit, wherein the memory isdisposed between the processing circuit and the fourth side.
 8. Thecircuit device according to claim 4, further comprising a digitalinterface terminal electrically coupled to the processing circuit,wherein the digital interface terminal is disposed between theprocessing circuit and the fourth side.
 9. The circuit device accordingto claim 4, further comprising a buffer circuit buffering theoscillation signal and outputting the oscillation signal to an outside,wherein when an opposite direction of the second direction is defined asa third direction, the buffer circuit is disposed on the third directionside of the oscillation signal generation circuit.
 10. The circuitdevice according to claim 4, further comprising an oven control circuitcontrolling a temperature of the resonator, wherein when an oppositedirection of the second direction is defined as a third direction, theoven control circuit is disposed on the third direction side of the A/Dconversion circuit.
 11. The circuit device according to claim 4, furthercomprising a PLL circuit generating and outputting a clock signalobtained by multiplying the oscillation signal, wherein when an oppositedirection of the second direction is defined as a third direction, thePLL circuit is disposed on the third direction side of the A/Dconversion circuit.
 12. A circuit device comprising: an A/D conversioncircuit A/D-converting a temperature detection voltage from atemperature sensor to output temperature detection data; processingcircuit performing temperature compensation processing of an oscillationfrequency based on the temperature detection data, to generate andoutput frequency control data of the oscillation frequency; and anoscillation signal generation circuit generating an oscillation signalof the oscillation frequency set by the frequency control data, usingthe frequency control data and a resonator, wherein the circuit devicehas a first side, a second side opposite to the first side, a third sidecrossing the first side, and a fourth side opposite to the third side,and when a direction from the first side to the second side is definedas a first direction and a direction from the third side to the fourthside is defined as a second direction, the oscillation signal generationcircuit is disposed on the first direction side of the A/D conversioncircuit, the processing circuit is disposed on the second direction sideof the A/D conversion circuit and the oscillation signal generationcircuit, the A/D conversion circuit is disposed at a position having ashorter distance from the first side compared to a distance from thesecond side, and the oscillation signal generation circuit is disposedat a position having a shorter distance from the second side compared toa distance from the first side.
 13. An oscillator comprising the circuitdevice according to claim 1, and the resonator.
 14. An electronicapparatus comprising the circuit device according to claim
 1. 15. Avehicle comprising the circuit device according to claim 1.